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edition 2011-7-04 published by infineon technologies ag, 81726 munich, germany, ? 2007 infineon technologies ag. all rights reserved. legal disclaimer the information given in this document shall in no event be regarded as a guarantee of conditions or characteristics. with respect to any examples or hints given herein, any typical values stated herein and/or any information regarding the application of the device, infineon technologies hereby disclaims any and all warranties and liabilities of any kind, including without limitation, warranties of non-infringement of intellectual property rights of any third party. information for further information on technology, delivery terms and conditions and prices, please contact your nearest infineon technologies office (www.infineon.com ). warnings due to technical requirements, components may contain dangerous substances. for information on the types in question, please contact your nearest infineon technologies office. infineon technologies components may be used in life-support devices or systems only with the express written approval of infineon technologies, if a failure of such components can reasonably be expected to cause the failure of that life-support device or system or to affect the safety or effectiveness of that device or system. life support devices or systems are intended to be implanted in the human body or to support and/or maintain and sustain and/or protect human life. if they fail, it is reasonable to assume that the health of the user or other persons may be endangered. for questions on technology, delivery and prices please contact the infineon technologies offices in germany or the infineon technologies companies and representatives worldwide: see our webpage at http:// www.infineon.com coolmos ? , coolset ? are trademarks of infineon technologies ag. coolset ? -f3r ice3bxx65j revision history: 2011-7-04 datasheet previous version: 2.5 page subjects (major changes since last revision) add ice3b2065j 23 revised dip-8 outline dimension
type package marking v ds f osc r dson 1) 1) typ @ t=25c 230vac 15% 2) 2) calculated maximum input power rating at t a =75c, t j =125c and without copper area as heat sink 85-265 vac 2) ice3b0365j pg-dip-8 ice3b0365j 650v 67khz 6.45w 22w 10w ice3b0565j pg-dip-8 ice3b0565j 650v 67khz 4.70w 25w 12w ice3b1565j pg-dip-8 ice3b1565j 650v 67khz 1.70w 42w 20w ice3br2065j pg-dip-8 ice3b2065j 650v 67khz 0.92w 57w 28w version 2.6 3 4 jul 2011 coolset ? -f3r ice3bxx65j off-line smps current mode controller with integrated 650v coolmos ? and startup cell (frequency jitter mode) in dip-8 pg-dip-8 product highlights ? active burst mode to reach the lowest standby power requirements < 100mw ? adjustable blanking window for high load jumps to increase reliability ? frequency jittering for low emi ? pb-free lead plating, rohs compilant features ? 650v avalanche rugged coolmos ? with built in switchable startup cell ? active burst mode for lowest standby power @ light load controlled by feedback signal ? fast load jump response in active burst mode ? 67 khz fixed switching frequency ? auto restart mode for over temperature detection ? auto restart mode for overvoltage detection ? auto restart mode for overload and open loop ? auto restart mode for vcc undervoltage ? user defined soft start ? minimum of external components required ? max duty cycle 75% ? overall tolerance of current limiting < 5% ? internal leading edge blanking ? bicmos technology provides wide vcc range ? frequency jittering for low emi description the coolset ? -f3(jitter version) meets the requirements for off-line battery adapters and low cost smps for the lower power range. by use of a bicmos technology a wide vcc range up to 26v is provided. this covers the changes in the auxiliary supply voltage if a cv/cc regulation is implemented on the secondary side. furthermore an active burst mode is integrated to fullfill the lowest standby power requirements <100mw at no load and v in = 270vac. as during active burst mode the controller is always active there is an immediate response on load jumps possible without any black out in the smps. in active burst mode the ripple of the output voltage can be reduced <1%. furthermore auto restart mode is entered in case of overtemperature, vcc overvoltage, output open loop or overload and vcc undervoltage. by means of the internal precise peak current limitation, the dimension of the transformer and the secondary diode can be lowered which leads to more cost efficiency. c softs c vcc c bulk converter dc output + snubber power management pw m controller current mode 85 ... 270 vac typical application r sense softs fb gnd active burst mode auto restart mode control unit - cs vcc startup cell precise low tolerance peak current limitation drain coolset ? -f3 (jitter version) depl. coolmos ?
coolset ? -f3r ice3bxx65j table of contents page version 2.6 4 4 jul 2011 1 pin configuration and functionality . . . . . . . . . . . . . . . . . . . . . . . . . . . . .5 1.1 pin configuration with pg-dip-8 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .5 1.2 pin functionality . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .5 2 representative blockdiagram . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .6 3 functional description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .7 3.1 introduction . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .7 3.2 power management . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .7 3.3 startup phase . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .8 3.4 pwm section . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .9 3.4.1 oscillator . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .9 3.4.2 pwm-latch ff1 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .9 3.4.3 gate driver . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .9 3.5 current limiting . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .10 3.5.1 leading edge blanking . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .10 3.5.2 propagation delay compensation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .10 3.6 control unit . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .11 3.6.1 adjustable blanking window . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .11 3.6.2 active burst mode . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .12 3.6.2.1 entering active burst mode . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .12 3.6.2.2 working in active burst mode . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .12 3.6.2.3 leaving active burst mode . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .12 3.6.3 protection modes . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .13 3.6.3.1 auto restart mode . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .14 4 electrical characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .15 4.1 absolute maximum ratings . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .15 4.2 operating range . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .16 4.3 characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .16 4.3.1 supply section . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .16 4.3.2 internal voltage reference . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .17 4.3.3 pwm section . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .17 4.3.4 control unit . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .17 4.3.5 current limiting . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .18 4.3.6 coolmos ? section . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .18 5 temperature derating curve . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .20 6 outline dimension . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .23 7 marking . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .24 8 schematic for recommended pcb layout . . . . . . . . . . . . . . . . . . . . . . . .26
version 2.6 5 4 jul 2011 coolset ? -f3r ice3bxx65j 1 pin configuration and functionality 1.1 pin configuration with pg-dip-8 figure 1 pin configuration pg-dip-8(top view) note: pin 4 and 5 are shorted within the dip package. 1.2 pin functionality softs (soft start, auto restart & frequency jittering control) the softs pin combines the function of soft start during start up and error detection for auto restart mode. these functions are implemented and can be adjusted by means of an external capacitor at softs to ground. this capacitor also provides an adjustable blanking window for high load jumps, before the ic enters into auto restart mode. furthermore this pin is also used to control the period of frequency jittering during normal load. fb (feedback) the information about the regulation is provided by the fb pin to the internal protection unit and to the internal pwm-comparator to control the duty cycle. the fb- signal controls in case of light load the active burst mode of the controller. cs (current sense) the current sense pin senses the voltage developed on the series resistor inserted in the source of the integrated coolmos ? . if cs reaches the internal threshold of the current limit comparator, the driver output is immediately switched off. furthermore the current information is provided for the pwm- comparator to realize the current mode. drain (drain of integrated coolmos ? ) pin drain is the connection to the drain of the internal coolmos tm . vcc (power supply) the vcc pin is the positive supply of the ic. the operating range is between 10.3v and 26v. gnd (ground) the gnd pin is the ground of the controller. pin symbol function 1 softs soft-start 2 fb feedback 3 cs current sense/ 650v 1) coolmos ? source 4 drain 650v 1) coolmos ? drain 1) at t j = 110c 5 drain 650v 1) coolmos ? drain 6 n.c. not connected 7 vcc controller supply voltage 8 gnd controller ground package pg-dip-8 1 6 7 8 4 3 2 5 gndsofts fb cs vcc n.c drain drain
version 2.6 6 4 jul 2011 coolset ? -f3r ice3bxx65j 2 representative blockdiagram figure 2 representative blockdiagram
version 2.6 7 4 jul 2011 coolset ? -f3r ice3bxx65j 3 functional description all values which are used in the functional description are typical values. for calculating the worst cases the min/max values which can be found in section 4 electrical characteristics have to be considered. 3.1 introduction coolset ? -f3 jitter version is the further development of the coolset ? -f2 to meet the requirements for the lowest standby power at minimum load and no load conditions. a new fully integrated standby power concept is implemented into the ic in order to keep the application design easy. compared to coolset ? -f2 no further external parts are needed to achieve the lowest standby power. an intelligent active burst mode is used for this standby mode. after entering this mode there is still a full control of the power conversion by the secondary side via the same optocoupler that is used for the normal pwm control. the response on load jumps is optimized. the voltage ripple on v out is minimized. v out is further on well controlled in this mode. the usually external connected rc-filter in the feedback line after the optocoupler is integrated in the ic to reduce the external part count. furthermore a high voltage startup cell is integrated into the ic which is switched off once the undervoltage lockout on-threshold of 18v is exceeded. this startup cell is part of the integrated coolmos ? . the external startup resistor is no longer necessary as this startup cell is connected to the drain. power losses are therefore reduced. this increases the efficiency under light load conditions drastically. the soft-start capacitor is also used for providing an adjustable blanking window for high load jumps. during this time window the overload detection is disabled. with this concept no further external components are necessary to adjust the blanking window. an auto restart mode is implemented in the ic to reduce the average power conversion in the event of malfunction or unsafe operating condition in the smps system. this feature increases the system?s robustness and safety which would otherwise lead to a destruction of the smps. once the malfunction is removed, normal operation is automatically initiated after the next start up phase. the internal precise peak current limitation reduces the costs for the transformer and the secondary diode. the influence of the change in the input voltage on the power limitation can be avoided together with the integrated propagation delay compensation. therefore the maximum power is nearly independent on the input voltage which is required for wide range smps. there is no need for an extra over-sizing of the smps, e.g. the transformer or the secondary diode. 3.2 power management figure 3 power management the undervoltage lockout monitors the external supply voltage v vcc . when the smps is plugged to the main line the internal startup cell is biased and starts to charge the external capacitor c vcc which is connected to the vcc pin. the vcc charge current that is provided by the startup cell from the drain pin is 1.05ma. when v vcc exceeds the on-threshold v ccon =18v, bias circuit is switched on. then the startup cell is switched off by the undervoltage lockout and therefore no power losses present due to the connection of the startup cell to the drain voltage. to avoid uncontrolled ringing at switch-on a hysteresis is implemented. the switch-off of the controller can only take place after active mode was entered and v vcc falls below 10.3v. the maximum current consumption before the controller is activated is about 300ua. internal bias voltage reference power management 5v vcc undervoltage lockout 18v 10.3 t1 power-down reset softs active burst mode auto restart mode startup cell drain
coolset ? -f3r ice3bxx65j version 2.6 8 4 jul 2011 when v vcc falls below the off-threshold v ccoff =10.3v the bias circuit is switched off and the power down reset let t1 discharging the soft-start capacitor c softs at pin softs. thus it is ensured that at every startup cycle the voltage ramp at pin softs starts at zero. the bias circuit is switched off if auto restart mode is entered. the current consumption is then reduced to 300ua. once the malfunction condition is removed, this block will then turn back on. the recovery from auto restart mode does not require disconnecting the smps from the ac line. when active burst mode is entered, some internal bias is switched off in order to reduce the current consumption to about 500ua while keeping a comparator (which trigger if v fb has exceeded 3.61v) and the soft start capacitor clamped at 3.0 v as this is necessary in this mode. 3.3 startup phase figure 4 soft start at the beginning of the startup phase, the ic provides a soft start duration whereby it controls the maximum primary current by means of a duty cycle limitation. a capacitor c softs in combination with the internal pull up resistor r softs determines the duty cycle until v softs exceeds 3.1v. when the soft start begins, c softs is immediately charged up to approx. 0.8v by t2. therefore the soft start phase takes place between 0.8v and 3.1v. above v softss = 3.1v there is no longer duty cycle limitation dc max which is controlled by comparator c7 since comparator c2 blocks the gate g7 (see figure 5).this maximum charge current in the very first stage when v softs is below 0.8v, is limited to 0.9ma. figure 5 startup phase by means of this extra charge stage, there is no delay in the beginning of the startup phase when there is still no switching. furthermore soft start is finished at 3.1v to have faster the maximum power capability. the duty cycles dc 1 and dc 2 are depending on the mains and the primary inductance of the transformer. the limitation of the primary current by dc 2 is related to v softs = 3.1v. but dc 1 is related to a maximum primary current which is limited by the internal current limiting with cs = 1v. therefore the maximum startup phase is divided into a soft start phase until t1 and a phase from t1 until t2 where maximum power is provided if demanded by the fb signal. soft-start comparator soft start & g7 c7 c softs r softs t2 3.25k ? 5v t3 0.8v softs gate driver 0.6v x3.2 pwm op cs 3.1v c2 freq jitter charging current i fj freq jitter discharging current i fj freq jitter control dc max dc 1 dc 2 t t v softs max. soft start phase 0.8v 3.1v 4.0v max. startup phase t1 t2
coolset ? -f3r ice3bxx65j version 2.6 9 4 jul 2011 3.4 pwm section figure 6 pwm section 3.4.1 oscillator and jittering the oscillator generates a fixed frequency with frequency jittering of 4% from the fixed frequency (which is 2.7khz from 67khz) at a jittering period t fj . the switching frequency is f switch = 67khz. a resistor, a capacitor and a current source and current sink which determine the frequency are integrated. the charging and discharging current of the implemented oscillator capacitor are internally trimmed, in order to achieve a very accurate switching frequency. the ratio of controlled charge to discharge current is adjusted to reach a maximum duty cycle limitation of d max =0.75. once the soft start period is over and when the ic goes into normal mode, the soft start capacitor will be charged and discharged through internal current source, i fj to generate a triangular waveform with a jittering period t fj which is externally adjustable by the soft start capacitor, c softs (see figure 4). t fj = k fj * c softs where k fj is a constant = 4 ms/uf eg. t fj = 4 ms if c softs = 1uf 3.4.2 pwm-latch ff1 the oscillator clock output provides a set pulse to the pwm-latch when initiating the internal coolmos ? conduction. after setting the pwm-latch can be reset by the pwm comparator, the soft start comparator or the current-limit comparator. in case of resetting the driver is shut down immediately. 3.4.3 gate driver the gate driver is a fast totem pole gate drive which is designed to avoid cross conduction currents. the gate driver is active low at voltages below the undervoltage lockout threshold v vccoff . figure 7 gate driver oscillator duty cycle max gate driver 0.75 clock & g9 1 g8 pwm section ff1 r s q gate soft start comparator pwm comparator current limiting frequency jitter softs vcc 1 pwm-latch depl. coolmos ? gate driver gate
coolset ? -f3r ice3bxx65j version 2.6 10 4 jul 2011 3.5 current limiting figure 8 current limiting there is a cycle by cycle current limiting realized by the current-limit comparator c10 to provide an overcurrent detection. the source current of the integrated coolmos ? is sensed via an external sense resistor r sense . by means of r sense the source current is transformed to a sense voltage v sense which is fed into the pin cs. if the voltage v sense exceeds the internal threshold voltage v csth the comparator c10 immediately turns off the gate drive by resetting the pwm latch ff1. a propagation delay compensation is added to support the immediate shut down without delay of the integrated internal coolmos ? in case of current limiting. the influence of the ac input voltage on the maximum output power can thereby be avoided. to prevent the current limiting from distortions caused by leading edge spikes a leading edge blanking is integrated in the current sense path for the comparators c10, c12 and the pwm-op. the output of comparator c12 is activated by the gate g10 if active burst mode is entered. once activated the current limiting is thereby reduced to 0.32v. this voltage level determines the power level when the active burst mode is left if there is a higher power demand. 3.5.1 leading edge blanking figure 9 leading edge blanking each time when the integrated internal coolmos ? is switched on a leading edge spike is generated due to the primary-side capacitances and secondary-side rectifier reverse recovery time. this spike can cause the gate drive to switch off unintentionally. to avoid a premature termination of the switching pulse, this spike is blanked out with a time constant of t leb = 220ns. during this time, the gate drive will not be switched off. 3.5.2 propagation delay compensation in case of overcurrent detection, the switch-off of the integrated internal coolmos ? is delayed due to the propagation delay of the circuit. this delay causes an overshoot of the peak current i peak which depends on the ratio of di/dt of the peak current (see figure 10). figure 10 current limiting the overshoot of signal2 is bigger than of signal1 due to the steeper rising waveform. this change in the slope is depending on the ac input voltage. propagation delay compensation is integrated to limit the overshoot dependency on di/dt of the rising primary current. that means the propagation delay time between exceeding the current sense threshold v csth and the switch off of the integrated inernal coolmos ? is compensated over temperature within a wide range. current limiting c10 c12 & 0.32v g10 propagation-delay compensation v csth active burst mode pwm latch ff1 10k ? d1 1pf pwm-op cs leading edge blanking 220ns t v sense v csth t leb = 220ns t i sense i limit t propagation delay i overshoot1 i peak1 signal1signal2 i overshoot2 i peak2
coolset ? -f3r ice3bxx65j version 2.6 11 4 jul 2011 current limiting is now possible in a very accurate way. e.g. i peak = 0.5a with r sense = 2. without propagation delay compensation the current sense threshold is set to a static voltage level v csth =1v. a current ramp of di/dt = 0.4a/s, that means dv sense /dt = 0.8v/s, and a propagation delay time of i.e. t propagation delay =180ns leads then to an i peak overshoot of 14.4%. by means of propagation delay compensation the overshoot is only about 2% (see figure 11). figure 11 overcurrent shutdown the propagation delay compensation is realized by means of a dynamic threshold voltage v csth (see figure 12). in case of a steeper slope the switch off of the driver is earlier to compensate the delay. figure 12 dynamic voltage threshold v csth 3.6 control unit the control unit contains the functions for active burst mode and auto restart mode. the active burst mode and the auto restart mode are combined with an adjustable blanking window which is depending on the external soft start capacitor. by means of this adjustable blanking window, the ic avoids entering into these two modes accidentally. furthermore it also provides a certain time whereby the overload detection is delayed. this delay is useful for applications which normally works with a low current and occasionally require a short duration of high current. 3.6.1 adjustable blanking window figure 13 adjustable blanking window v softs swings between 3.2v and 3.6v after the smps is settled and s2 is on while s3 is off, this is due to the frequency jittering function that is making use of the soft start pin. if overload occurs v fb is exceeding 4.5v. auto restart mode can?t be entered as the gate g5 is still blocked by the comparator c3. but after v fb has 0,9 0,95 1 1,05 1,1 1,15 1,2 1,25 1,3 0 0,2 0,4 0,6 0,8 1 1,2 1,4 1,6 1,8 2 with compensation without compensation dt dv sense s v ? s e n s e v v t v csth v osc signal1 signal2 v sense propagation delay max. duty cycle off time t c3 4.0v c4 4.5v c5 1.35v & g5 & g6 3.0v s1 control unit active burst mode auto restart mode r softs 5v softs fb frequency jitter s2 s3
coolset ? -f3r ice3bxx65j version 2.6 12 4 jul 2011 exceeded 4.5v the switch s2 is opened and s3 is closed. the external soft start capacitor can now be charged further by the integrated pull up resistor r softs via switch s3. the comparator c3 releases the gates g5 and g6 once v softs has exceeded 4.0v. therefore there is no entering of auto restart mode possible during this charging time of the external capacitor c softs . the same procedure happens to the external soft start capacitor if a low load condition is detected by comparator c5 when v fb is falling below 1.35v. only after v softs has exceeded 4.0v and v fb is still below 1.35v active burst mode is entered. 3.6.2 active burst mode the controller provides active burst mode for low load conditions at v out . active burst mode increases significantly the efficiency at light load conditions while supporting a low ripple on v out and fast response on load jumps. during active burst mode which is controlled only by the fb signal the ic is always active and can therefore immediately response on fast changes at the fb signal. the startup cell is kept switched off to avoid increased power losses for the self supply. figure 14 active burst mode the active burst mode is located in the control unit. figure 14 shows the related components. 3.6.2.1 entering active burst mode the fb signal is always observed by the comparator c5 if the voltage level falls below 1.35v. in that case the switch s1 and s2 is released which allows the capacitor c softs to be charged via s3 starting from the swinging voltage level between 3.2v and 3.6v in normal operating mode. if v softs exceeds 4.0v the comparator c3 releases the gate g6 to enter the active burst mode. the time window that is generated by combining the fb and softs signals with gate g6 avoids a sudden entering of the active burst mode due to large load jumps. this time window can be adjusted by the external capacitor c softs . after entering active burst mode a burst flag is set and the internal bias is switched off in order to reduce the current consumption of the ic down to approx. 500ua. also, switch s1 is closed to clamped the soft start voltage to 3.0v. in this off state phase the ic is no longer self supplied so that therefore c vcc has to provide the vcc current (see figure 15). furthermore gate g11 is then released to start the next burst cycle once v fb has 3.0v exceeded. it has to be ensured by the application that the vcc remains above the undervoltage lockout level of 10.3v to avoid that the startup cell is accidentally switched on. otherwise power losses are significantly increased. the minimum vcc level during active burst mode is depending on the load conditions and the application. the lowest vcc level is reached at no load conditions at v out . 3.6.2.2 working in active burst mode after entering the active burst mode the fb voltage rises as v out starts to decrease due to the inactive pwm section. comparator c6a observes the fb signal if the voltage level 3.61v is exceeded. in that case the internal circuit is again activated by the internal bias to start with switching. as now in active burst mode the gate g10 is released the current limit is only 0.32v to reduce the conduction losses and to avoid audible noise. if the load at v out is still below the starting level for the active burst mode the fb signal decreases down to 3.0v. at this level c6b deactivates again the internal circuit by switching off the internal bias. the gate g11 is released as after entering active burst mode the burst flag is set. if working in active burst mode the fb voltage is changing like a saw tooth between 3.0v and 3.61v (see figure 15). 3.6.2.3 leaving active burst mode the fb voltage immediately increases if there is a high load jump. this is observed by comparator c4. as the current limit is ca. 32% during active burst mode a certain load jump is needed that fb can exceed 4.5v. at this time c4 resets the active burst mode which also c3 4.0v c4 4.5v c6a 3.61v c5 1.35v fb control unit active burst mode 3.0v s1 internal bias r softs 5v softs & g10 current limiting & g6 c6b 3.0v & g11 frequency jitter s2 s3
coolset ? -f3r ice3bxx65j version 2.6 13 4 jul 2011 blocks c12 by the gate g10. maximum current can now be provided to stabilize v out . figure 15 signals in active burst mode 3.6.3 protection modes the ic provides several protection features that increase the smps system?s robustness and safety. the following table shows the possible system failures and the corresponding protection modes. 3.6.3.1 auto restart mode i figure 16 auto restart mode i the vcc voltage is observed by comparator c13 if 20.5v is exceeded. the output of c13 is combined with both the output of c3 which checks for v softs < 4.0v and the output of c4 which checks for v fb > 4.5v. therefore the overvoltage detection can only be active during soft start phase (v softs < 4.0v) and when fb signal is outside the operating range > 4.5v. this means any 1.35v 3.61v 4.5v v fb 3.0v 4.0v v softs t t 0.32v 1.0v v cs 10.3v v vcc t t 500ua i vcc t 2ma v out t max. ripple < 1% blanking window current limit level during active burst mode 3.0v entering active burst mode leaving active burst mode 3.6v~ 3.2v vcc overvoltage auto restart mode i over temperature auto restart mode i overload auto restart mode ii open loop auto restart mode ii vcc undervoltage auto restart mode ii short optocoupler auto restart mode ii c3 spike blanking 8.0 us thermal shutdown t j >140c auto restart mode internal bias control unit c13 20.5v vcc c4 4.5v fb 4.0v softs & g12 & g13 ff2 r s q uvlo
coolset ? -f3r ice3bxx65j version 2.6 14 4 jul 2011 small voltage overshoots of v vcc during normal operating cannot trigger the auto restart mode i. in order to ensure system reliability and prevent any false activation, a blanking time is implemented before the ic can enter into the auto restart mode i. the output of the vcc overvoltage detection is fed into a spike blanking with a time constant of 8.0us. the other fault detection which can result in the auto restart mode i and has this 8.0us blanking time is the overtemperature detection. this block checks for a junction temperature of higher than 140c for malfunction operation. once auto restart mode is entered, the internal bias is switched off in order to reduce the current consumption of the ic as much as possible. in this mode, the average current consumption is only 300ua as the only working blocks are the reference block and the undervoltage lockout(uvlo) which controls the startup cell by switching on/off at v vccon /v vccoff . as there is no longer a self supply by the auxiliary winding, vcc starts to drop. the uvlo switches on the integrated startup cell when vcc falls below 10.3v. it will continue to charge vcc up to 18v whereby it is switched off again and the ic enters into the start up phase. as long as all fault conditions have been removed, the ic will automatically power up as usual with switching cycle at the gate output after soft start duration. thus the name auto restart mode. 3.6.3.2 auto restart mode ii figure 17 auto restart mode ii in case of overload or open loop, fb exceeds 4.5v which will be observed by c4. at this time, the external soft start capacitor can now be charged further by the integrated pull up resistor r softs via switch s3 (see figure 13). if v softs exceeds 4.0v which is observed by c3, auto restart mode ii is entered as both inputs of the gate g5 are high. this charging of the soft start capacitor from 3.2v~3.6v to 4.0v defines a blanking window which prevents the system from entering into auto restart mode ii unintentionally during large load jumps. in this event, fb will rise close to 5.0v for a short duration before the loop regulates with fb less than 4.5v. this is the same blanking time window as for the active burst mode and can therefore be adjusted by the external c softs . in case of vcc undervoltage, ie. vcc falls below 10.3v, the ic will be turned off with the startup cell charging vcc as described earlier in this section. once vcc is charged above 18v, the ic will start a new startup cycle. the same procedure applies when the system is under short optocoupler fault condition, as it will lead to vcc undervoltage. c3 4.0v c4 4.5v & g5 control unit softs internal bias auto restart mode fb
coolset ? -f3r ice3bxx65j version 2.6 15 4 jul 2011 4 electrical characteristics note: all voltages are measured with respect to ground (pin 8). the voltage levels are valid if other ratings are not violated. 4.1 absolute maximum ratings note: absolute maximum ratings are defined as ratings, which when being exceeded may lead to destruction of the integrated circuit. for the same reason make sure, that any capacitor that will be connected to pin 7 (vcc) is discharged before assembling the application circuit. parameter symbol limit values unit remarks min. max. drain source voltage v ds - 650 v t j = 110c pulse drain current, t p limited by max. t j =150c ice3b0365j i d_puls1 - 1.6 a ice3b0565j i d_puls2 - 2.3 a ice3b1565j i d_puls3 - 6.1 a ice3b2065j i d_puls4 - 10.3 a avalanche energy, repetitive t ar limited by max. t j =150c 1) 1) repetetive avalanche causes additional power losses that can be calculated as p av =e ar * f ice3b0365j e ar1 - 0.005 mj ice3b0565j e ar2 - 0.01 mj ice3b1565j e ar3 - 0.15 mj ice3b2065j e ar4 - 0.4 mj avalanche current, repetitive t ar limited by max. t j =150c 1) ice3b0365j i ar1 - 0.3 a ice3b0565j i ar2 - 0.5 a ice3b1565j i ar3 - 1.5 a ice3b2065j i ar4 - 2.0 a vcc supply voltage v vcc -0.3 27 v fb voltage v fb -0.3 5.0 v softs voltage v softs -0.3 5.0 v cs voltage v cs -0.3 5.0 v junction temperature t j -40 150 c controller & coolmos ? storage temperature t s -55 150 c thermal resistance junction-ambient r thja - 90 k/w pg-dip-8 esd capability v esd - 2 kv human body model 2) 2) according to eia/jesd22-a114-b (discharging a 100pf capacitor through a 1.5k w series resistor)
version 2.6 16 4 jul 2011 coolset ? -f3r ice3bxx65j 4.2 operating range note: within the operating range the ic operates as described in the functional description. 4.3 characteristics 4.3.1 supply section note: the electrical characteristics involve the spread of values guaranteed within the specified supply voltage and junction temperature range t j from ? 25 o c to 130 o c. typical values represent the median values, which are related to 25c. if not otherwise stated, a supply voltage of v cc = 18 v is assumed. parameter symbol limit values unit remarks min. max. vcc supply voltage v vcc v vccoff 26 v junction temperature of controller t jcon -25 130 c max value limited due to integrated thermal shut down junction temperature of coolmos ? t jcoolmos -25 150 c parameter symbol limit values unit test condition min. typ. max. start up current i vccstart - 300 450 m a v vcc = 17v vcc charge current i vcccharge1 - - 5.0 ma v vcc = 0v i vcccharge2 0.55 1.05 1.60 ma v vcc = 1v i vcccharge3 - 0.88 - ma v vcc = 17v leakage current of start up cell & coolmos i startleak - 0.2 50 m a v drain = 450v at t j = 100c supply current with inactive gate ice3b0365j ice3b0565j ice3b1565j i vccsup_ng1 - 1.7 2.5 ma soft start pin is open ice3b2065j i vccsup_ng2 - 3.3 4.2 ma supply current with active gate i vccsup_g - 2.5 3.6 ma v softs = 3.0v i fb = 0 supply current in auto restart mode with inactive gate i vccrestart - 300 - m a i fb = 0 i softs = 0 supply current in active burst mode with inactive gate i vccburst1 - 500 950 ua v fb = 2.5v v softs = 3.0v i vccburst2 - 500 950 ua v vcc = 11.5v v fb = 2.5v v softs = 3.0v vcc turn-on threshold vcc turn-off threshold vcc turn-on/off hysteresis v vccon v vccoff v vcchys 17.0 9.6 - 18.0 10.3 7.7 19.0 11.0 - v v v
coolset ? -f3r ice3bxx65j version 2.6 17 4 jul 2011 4.3.2 internal voltage reference 4.3.3 pwm section 4.3.4 control unit parameter symbol limit values unit test condition min. typ. max. trimmed reference voltage v ref 4.90 5.00 5.10 v measured at pin fb i fb = 0 parameter symbol limit values unit test condition min. typ. max. fixed oscillator frequency f osc3 58 67 76 khz f osc4 62 67 74.5 khz t j = 25c frequency jittering range f delta - 2.7 - khz t j = 25c max. duty cycle d max 0.70 0.75 0.80 min. duty cycle d min 0 - - v fb < 0.3v pwm-op gain a v 3.0 3.2 3.4 max. level of voltage ramp v max-ramp - 0.6 - v v fb operating range min level v fbmin - 0.5 - v v fb operating range max level v fbmax - - 4.3 v cs=1v limited by comparator c4 1) 1) this parameter is not subject to production test - verified by design/characterization feedback pull-up resistor r fb 9 14 22 k w soft-start pull-up resistor r softs 30 45 62 k w parameter symbol limit values unit test condition min. typ. max. deactivation level for softs comparator c7 by c2 v softsc2 2.98 3.10 3.22 v v fb = 5v clamped v softs voltage during burst mode v softsclmp_bm 2.88 3.00 3.12 v activation limit of comparator c3 v softsc3 3.85 4.00 4.15 v v fb = 5v softs startup current i softsstart - 0.9 - ma v softs = 0v over load & open loop detection limit for comparator c4 v fbc4 4.33 4.50 4.67 v v softs = 4.5v active burst mode level for comparator c5 v fbc5 1.23 1.35 1.43 v v softs = 4.5v active burst mode level for comparator c6a v fbc6a 3.48 3.61 3.76 v after active burst mode is entered
version 2.6 18 4 jul 2011 coolset ? -f3r ice3bxx65j note: the trend of all the voltage levels in the control unit is the same regarding the deviation except v vccovp 4.3.5 current limiting 4.3.6 coolmos ? section active burst mode level for comparator c6b v fbc6b 2.88 3.00 3.12 v after active burst mode is entered overvoltage detection limit v vccovp 19.5 20.5 21.5 v v fb = 5v, v softs = 3v thermal shutdown 1) t jsd 130 140 150 c spike blanking t spike - 8.0 - m s 1) the parameter is not subject to production test - verified by design/characterization parameter symbol limit values unit test condition min. typ. max. peak current limitation (incl. propagation delay time) (see figure 11) v csth 1.01 1.06 1.11 v dv sense / dt = 0.6v/ m s peak current limitation during active burst mode v cs2 0.27 0.32 0.37 v leading edge blanking t leb - 220 - ns v softs = 3.0v cs input bias current i csbias -1.0 -0.2 0 a v cs = 0v parameter symbol limit values unit test condition min. typ. max. drain source breakdown voltage v (br)dss 600 650 - - - - v v t j = 25c t j = 110c drain source on-resistance ice3b0365j r dson1 - - 6.45 13.70 7.50 17.00 w w t j = 25c t j = 125c 1) at i d = 0.3a ice3b0565j r dson2 - - 4.70 10.00 5.44 12.50 w w t j = 25c t j = 125c 1) at i d = 0.5a ice3b1565j r dson3 - - 1.70 3.57 1.96 4.12 w w t j = 25c t j = 125c 1) at i d = 1.5a ice3b2065j r dson4 - - 0.92 1.93 1.05 2.22 w w t j = 25c t j = 125c 1) at i d = 2.0a effective output capacitance, energy related ice3b0365j c o(er)1 - 3.65 - pf v ds = 0v to 480v ice3b0565j c o(er)2 - 4.75 - pf ice3b1565j c o(er)3 - 11.63 - pf ice3b2065j c o(er)4 - 21 - pf
coolset ? -f3r ice3bxx65j version 2.6 19 4 jul 2011 rise time t rise - 30 2) - ns fall time t fall - 30 2) - ns 1) the parameter is not subject to production test - verified by design/characterization 2) measured in a typical flyback converter application
version 2.6 20 4 jul 2011 coolset ? -f3r ice3bxx65j 5 temperature derating curve figure 18 safe operating area ( soa ) curve for ice3b0365j figure 19 safe operating area ( soa ) curve for ice3b0565j
coolset ? -f3r ice3bxx65j version 2.6 21 4 jul 2011 figure 20 safe operating area ( soa ) curve for ice3b1565j figure 21 safe operating area ( soa ) curve for ice3b2065j
version 2.6 22 4 jul 2011 coolset ? -f3r ice3bxx65j figure 22 soa temperature derating coefficient curve
coolset ? -f3r ice3bxx65j version 2.6 23 4 jul 2011 6 outline dimension figure 23 pg-dip-8 ( pb-free lead plating platic dual-in-line outline ) pg-dip-8 (plastic dual in-line outline)
version 2.6 24 4 jul 2011 coolset ? -f3r ice3bxx65j 7 marking figure 24 marking for ice3b0365j figure 25 marking for ice3b0565j marking marking
coolset ? -f3r ice3bxx65j version 2.6 25 4 jul 2011 figure 26 marking for ice3b1565j figure 27 marking for ice3b2065j marking marking
version 2.6 26 4 jul 2011 coolset ? -f3r ice3bxx65j schematic for recommended pcb layout 8 schematic for recommended pcb layout figure 28 schematic for recommended pcb layout general guideline for pcb layout design using f3 coolset (refer to figure 26): 1. ?star ground ?at bulk capacitor ground, c11: ?star ground ?means all primary dc grounds should be connected to the ground of bulk capacitor c11 separately in one point. it can reduce the switching noise going into the sensitive pins of the coolset device effectively. the primary dc grounds include the followings. a. dc ground of the primary auxiliary winding in power transformer, tr1, and ground of c16 and z11. b. dc ground of the current sense resistor, r12 c. dc ground of the coolset device, gnd pin of ic11; the signal grounds from c13, c14, c15 and collector of ic12 should be connected to the gnd pin of ic11 and then ?star ?connect to the bulk capacitor ground. d. dc ground from bridge rectifier, br1 e. dc ground from the bridging y-capacitor, c4 2. high voltage traces clearance: high voltage traces should keep enough spacing to the nearby traces. otherwise, arcing would incur. a. 400v traces (positive rail of bulk capacitor c11) to nearby trace: > 2.0mm b. 600v traces (drain voltage of coolset ic11) to nearby trace: > 2.5mm 3. filter capacitor close to the controller ground: filter capacitors, c13, c14 and c15 should be placed as close to the controller ground and the controller pin as possible so as to reduce the switching noise coupled into the controller. guideline for pcb layout design when >3kv lightning surge test applied (refer to figure 26): 1. add spark gap spark gap is a pair of saw-tooth like copper plate facing each other which can discharge the accumulated charge during surge test through the sharp point of the saw-tooth plate. a. spark gap 3 and spark gap 4, input common mode choke, l1: gap separation is around 1.5mm (no safety concern)
coolset ? -f3r ice3bxx65j schematic for recommended pcb layout version 2.6 27 4 jul 2011 b. spark gap 1 and spark gap 2, live / neutral to ground: these 2 spark gaps can be used when the lightning surge requirement is >6kv. 230vac input voltage application, the gap separation is around 5.5mm 115vac input voltage application, the gap separation is around 3mm 2. add y-capacitor (c2 and c3) in the live and neutral to ground even though it is a 2-pin input 3. add negative pulse clamping diode, d11 to the current sense resistor, r12: the negative pulse clamping diode can reduce the negative pulse going into the cs pin of the coolset and reduce the abnormal behavior of the coolset. the diode can be a fast speed diode such as in4148. the principle behind is to drain the high surge voltage from live/neutral to ground without passing through the sensitive components such as the primary controller, ic11.
qualit?t hat fr uns eine umfassende bedeutung. wir wollen allen ihren ansprchen in der bestm?glichen weise gerecht werden. es geht uns also nicht nur um die produktqualit?t ? unsere anstrengungen gelten gleicherma?en der lieferqualit?t und logistik, dem service und support sowie allen sonstigen beratungs- und betreuungsleistungen. dazu geh?rt eine bestimmte geisteshaltung unserer mitarbeiter. total quality im denken und handeln gegenber kollegen, lieferanten und ihnen, unserem kunden. unsere leitlinie ist jede aufgabe mit ?null fehlern? zu l?sen ? in offener sichtweise auch ber den eigenen arbeitsplatz hinaus ? und uns st?ndig zu verbessern. unternehmensweit orientieren wir uns dabei auch an ?top? (time optimized processes), um ihnen durch gr??ere schnelligkeit den entscheidenden wettbewerbsvorsprung zu verschaffen. geben sie uns die chance, hohe leistung durch umfassende qualit?t zu beweisen. wir werden sie berzeugen. quality takes on an allencompassing significance at semiconductor group. for us it means living up to each and every one of your demands in the best possible way. so we are not only concerned with product quality. we direct our efforts equally at quality of supply and logistics, service and support, as well as all the other ways in which we advise and attend to you. part of this is the very special attitude of our staff. total quality in thought and deed, towards co-workers, suppliers and you, our customer. our guideline is ?do everything with zero defects?, in an open manner that is demonstrated beyond your immediate workplace, and to constantly improve. throughout the corporation we also think in terms of time optimized processes (top), greater speed on our part to give you that decisive competitive edge. give us the chance to prove the best of performance through the best of quality ? you will be convinced. h t t p : / / w w w . i n f i n e o n . c o m total quality management published by infineon technologies ag

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